Method and apparatus for controlling acoustic signal bandwidth in an ultrasonic diagnostic imaging system

ABSTRACT

An ultrasonic imaging system includes a receive beamformer that generates analog receive signals and a scan converter. A receive signal processing path interconnects the receive beamformer and the scan converter, and this processing path includes both an A/D converter characterized by a selectable sampling rate and at least one filter characterized by at least one filter parameter. The filter parameter is selected as a function of the sampling rate to provide enhanced image quality.

This application is a division of application Ser. No. 08/759,560, filedDec. 4, 1996, (pending).

BACKGROUND OF THE INVENTION

The present invention relates to ultrasound diagnostic imaging systems,and in particular to methods and systems for controlling the acousticsignal bandwidth in such systems.

Hedberg U.S. Pat. No. 5,396,285, assigned to the assignee of the presentinvention, discloses an improved receive signal processing path for aultrasound diagnostic imaging system. This improved processing pathutilizes programmable linear or nonlinear filters to provide an enhancedimage for display.

The present invention is directed to improved systems for controllingone or more programmable filters included in the receive signalprocessing path of such an imaging system.

SUMMARY OF THE INVENTION

This invention relates to an improvement to an ultrasound imaging systemof the type comprising an ultrasonic transducer operative to generatereceive signals indicative of sensed ultrasonic energy, a receive signalprocessing path responsive to the receive signal, and a scan converterresponsive to the receive signal processing path. According to a firstaspect of the invention, the receive signal processing path comprises atleast one filter characterized by at least one filter parameter, andmeans for selecting the filter parameter as a function of the samplingrate of an analog-to-digital (A/D) converter included in the receivesignal processing path, or as a function of an azimuthal line densitycharacteristic of the receive signal.

By automatically controlling the filter in response to the sampling rateof the A/D converter or azimuthal line density, signal bandwidth andimage quality can be preserved in the face of changes of the A/Dsampling rate or the azimuthal line density.

According to another aspect of this invention, a method is provided forprocessing analog receive signals generated by an ultrasonic transducerof an ultrasound imaging system prior to scan conversion. This methodcomprises the step of filtering the receive signals in analog or digitalform. The response characteristics of one or more filters are modifiedin response to changes in the sampling rate of an AND converter for thereceive signals, or as a function of an azimuthal line densitycharacteristic. In this way, the bandwidth and other spectral responsecharacteristics of the receive signals can be maintained at a desiredlevel in the face of changes in the sampling rate or the azimuthal linedensity.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a block diagram of an ultrasound imaging system thatincorporates a presently preferred embodiment of this invention.

FIG. 2 is a block diagram of the analog video filter of FIG. 1.

FIG. 3 is a block diagram of the digital azimuthal filter of FIG. 1.

FIG. 4 is a block diagram of the digital axial filter of FIG. 1.

FIGS. 5a, 5b and 5c illustrate the response characteristics of theanalog video filter, the digital axial filter, and the combination ofthe two filters, respectively, in one exemplary mode of operation.

DETAILED DESCRIPTION OF THE PRESENTLY PREFERRED EMBODIMENTS

Turning now to the drawings, FIG. 1 shows a block diagram of the receivesignal path of an ultrasonic imaging system. An analog receivebeamformer 1 receives radio frequency input signals from the elements ofa transducer array T, amplifies and converts these signals to anintermediate frequency (IF), coherently sums them together, and filtersthe output. The resultant receive signal is passed to a log amplifier 2and envelope detector 3 to generate video output signals for eachultrasound scan line. An analog axial video filter 4 filters each scanline prior to digital sampling of the signal by an analog-to-digitalconverter 5. The digitized scan line data are stored in a lineacquisition image memory 6, which can accumulate one or more completeframes of acoustic image data. A two-dimensional digital filter 7processes each frame of data. The filtered data are passed to a scanconverter 8, which supplies raster output video data for display on avideo monitor 9. The processing elements 1-7 between the transducer Tand the scan converter 8 form a receive signal processing path.

In the preferred embodiment, the two-dimensional filter 7 includes twocomponents: an FIR azimuthal filter 10, and a FIR range filter 11.Alternatively, the two-dimensional filter 7 can be implemented as asingle non-separable, two-dimensional filter, as described in theabove-identified Hedberq patent.

The video filter 4 and the 2-D digital filter 7 can be programmed foreither linear or nonlinear operation, as described below. Each is alsocapable of varying in bandwidth as a function of position in the image.In the preferred embodiment, the video filter axial bandwidth depends onthe line number of the ultrasound scan line to which the filter isapplied, and the azimuthal filter spatial bandwidth varies with bothscan line number and range position. In alternative embodiments,position and range information can be used to control the bandwidth ofboth analog and digital filters.

The filters 4, 10, and 11 are dynamically programmed with configurationdata and lookup table data by logic blocks 13, 14, and 15, respectively.These logic blocks are controlled by the filter control block 12, whichstores tables of filter parameters that determine the bandwidth of eachfilter, the degree of nonlinear behavior of each filter, and thevariation of bandwidth with line number for the video filter 4 or withline number and range for the azimuthal component of the 2-D filter 7.(To dynamically program the spatial variation of filter 4, the logicblock 13 receives the active scan line number as an input. To programthe spatial variation of the azimuthal filter 10, the azimuthal filteritself receives line number and range sample number as inputs, and theazimuthal logic block 14 receives the minimum and maximum line numberdepth as inputs. See FIG. 1.)

During normal usage of the ultrasound system, the operator may changecertain front panel controls which result in a change in one or more ofthe following quantities:

the AND sampling rate,

the line density,

the horizontal and vertical video pixel densities,

the center frequency,

the edge enhancement control setting.

The A/D sampling rate and line density affect the sampling grid in theacoustic domain (i.e., in the image data prior to scan conversion). Thevertical and horizontal pixel densities determine the sampling grid inthe display domain (i.e., in the displayed image after scan conversion).The center frequency and the edge enhancement control setting determinea desired level of lateral and axial resolution and edge enhancement orspatial smoothing. Whenever one or more of the above-listed quantitieschange, the filter control block 12 may select a new set of filterparameters in order to avoid aliasing during scan conversion and/or toachieve the appropriate lateral and axial bandwidths. The filter controlblock 12 accomplishes this function with an indexed table that linkseach set of filter parameters to a particular combination of the abovequantities. Further discussion of each of these quantities and of theindexing scheme follows.

A/D Sampling Rate

The A/D sampling rate determines the temporal separation betweenadjacent samples on a scan line in the acoustic domain. It is importantto use the A/D sampling rate as an input to configure the digital FIRrange filter 11, because the bandwidth of this filter depends on thesampling rate.

Two constraints are applied in determining the A/D sampling rate. First,the minimum sampling rate is selected to be greater than twice thebandwidth of the output of the video filter 4. Second, the total numberof samples collected per scan line is limited such that it does notexceed a limit N_(max) imposed by the finite size of the image memory 6allocated per scan line. This latter constraint imposes an upper boundon the sampling frequency in MHz of

    c*N.sub.max /(2*FOV),

where c is the speed of sound in tissue (1.54 mm/usec), and FOV is thedepth of the field of view in mm, i.e., the distance in mm between thestart and end depths of the displayed image.

In the preferred embodiment, the ultrasound imaging system supports anumber of sampling rates N_(r) which exceed the minimum determined bythe output bandwidth of the video filter 4. The sampling rate chosen isthe largest rate that is not greater than the upper bound imposed byN_(max). As the user changes the field of view, for example, by changingthe maximum depth of the image, by selecting and enlarging a portion ofthe image, or by deactivating such an enlargement function, the samplingrate may change.

The filter control block 12 assigns an index from 0to N_(r) -1 to eachof the N_(r) allowed sampling rates.

Line Density

The spacing between adjacent scan lines determines the spatial bandwidthof the azimuthal filter 10. Because the spacing may change with depth orwith lateral position for sector or Vector® image formats, theparameters which control the azimuthal filter 10 compensate for thesechanges in order to preserve consistent spatial bandwidth across theimage. For example, in a sector or Vector® format, less azimuthalsmoothing (or more sharpening) is needed deeper in the image where scanlines are farther apart than shallower in the image where scan lines arecloser together.

In the preferred embodiment, the spacing between scan lines can varywith operator control. Preserving image quality at different linedensities will in general require different azimuthal filter parametersets.

As an example of how line density may change, for some transducers, forwhich a high frame rate is desired, the ultrasound system may reduce theline density with a full view image while employing a higher linedensity when the operator selects and enlarges a portion of an image.The system may also reduce line density when the B-mode image is reducedin size to allow room on the screen for a pulsed wave Doppler display,an M-mode display, or other information. In this example, the number ofdifferent line densities N_(l) is 3, and the control block 12 assigns anindex from 0 to N_(l) -1 to each line density setting.

In other embodiments, the number of line density settings and theconditions under which line density changes may differ from thisexample.

Video Pixel Density

The vertical and horizontal video pixel densities, _(V) and _(H), arethe number of video pixels per mm of image in the vertical andhorizontal directions, respectively, as measured along the center scanline. Note that this is not the same as the number of pixels per mm ofthe monitor itself, i.e. distance is measured in the image, not in thephysical monitor.

In the axial direction, to avoid aliasing artifacts when scan convertingacoustic data along a line at an angle θ with respect to the vertical,the acoustic range data along the line should be bandlimited at afrequency (in MHz) less than

    c*.sub.V *cos(θ)/4.

In the lateral direction, the spatial bandwidth prior to scan conversionis determined by the beamwidth and the line spacing. For uniformlyspaced vertical scan lines with spacing s (in mm), if the pixel spacingis greater than the line spacing, then scan conversion imposes the needfor further restriction of the spatial bandwidth (in wavelengths/scanline) to less than

    s*.sub.H /2.

Similarly, for a sector or Vector® format, if the angle between lineschanges in such a way that the increments in sin (θ) are a uniform valueΔ, and the pixel spacing is greater than the line spacing, then thelateral spatial bandwidth at depth R should be restricted to

    R*Δ*.sub.H /2.

If the number of horizontal pixels per scan line exceeds 1, as it oftendoes in deeper portions of Vector® and sector formatted images, then thebandwidth of the azimuthal filter 10 may be expanded to counteract thesmoothing imposed by scan conversion interpolation, though care shouldbe taken to avoid excessively increasing the amplitude of image noise.

With these considerations, specific mutually exclusive domains of _(H)and _(V) are defined in the filter control block 12, and indices from 0to N_(p) -1 assigned to each of these N_(p) pixel domains. For example,one pixel domain could be used to store filter parameters appropriatefor the following values of _(H) and _(V:)

    s*.sub.H <1 and 0.6 MHz<c*.sub.V <0.7MHz

If the operator of the ultrasound machine changes the size of all or aportion of the image, or changes the maximum display depth of the image,the pixel density parameters may change, possibly leading to a change inthe active pixel domain.

The filter control block assigns an index from 0 to N_(p) -1 to each ofthe defined pixel domains.

Center Frequency

Transducers can typically be made to operate effectively at severaldifferent center frequencies. Often, the transducer bandwidth changeswith a change in center frequency. For this reason, for each centerfrequency, different filter response characteristics may be preferredfor the video filter 4 as well as the 2D filter 7. The filter controlblock 12 assigns each of the N_(f) receive center frequencies an indexfrom 0 to N_(f) -1.

Edge Enhancement Control Setting

In the preferred embodiment, a control of the front panel is availablewhich provides N_(e) choices of edge enhancement or smoothing. Personalpreferences regarding the degree of edge enhancement or smoothing varyfrom one operator to another. Moreover, many operators desire an imagewith more smoothing than is dictated by sampling considerations ineither the acoustic or scan converted grid. The filter control block 12assigns an index from 0 to N_(e) -1 to each edge setting.

Indexing of the Parameter Sets

There are a total of N_(r) *N_(l) *N_(p) *N_(f) *N_(e) uniquecombinations of the filter control quantities discussed above. Eachcombination is associated in the filter control block 12 with a specificset of filter parameters that determine the bandwidth, nonlinearity, andspatial variation of the video and 2-D filters 4, 7. A specificcombination of sampling rate, line skip setting, pixel density, centerfrequency, and edge enhancement control setting results in oneparticular combination of indices. For that combination, the controlblock 12 selects the associated filter parameter set, and each of thefilters is configured in a manner appropriate to that combination ofindices. As the operator changes front panel controls for the edgeenhancement control, center frequency, maximum depth of view, imageenlargement, or image size, some or all of the indices may change, a newset of filter parameters may then be selected, and a new filterconfiguration results.

Those skilled in the art will recognize that the indices for each of theinput quantities for the control block 12 need not start from 0, norneed they consist of sequential integers. The only requirement is thateach of the allowed input quantities be associated with a unique index.

Video Filter

The preferred embodiment of the analog video filter 4 is shown in FIG.2. The filter 4 includes a video low pass filter 29 with three bandwidthoptions, and a programmable three tap FIR filter that may be configuredfor either linear nonlinear operation. Hedberg U.S. Pat. No. 5,396,285provides a more detailed discussion of the video low pass filter 29(which corresponds to the filter 10 of FIG. 2 of the Hedberg patent) andthe elements 30-38 of the three tap FIR filter (which correspond to thesimilarly numbered elements of FIG. 3 of the Hedberg patent). TheHedberg patent is hereby incorporated by reference in its entirety forits description of these elements, as well as other elements describedbelow.

The filter control block 12 provides the following parameters to thefilter 4: low pass filter bandwidth selection, tap spacing, coefficientgain multiplier (constant, X1, X2, or X3), coefficient gain offset, andcoefficient gain saturation limit. In the most general implementation,each of these parameters can change with scan line number. In thepreferred embodiment the gain saturation limit and gain offset areprogrammed to vary with line number, such that the filter bandwidth isproportional to the cosine of the scan line angle.

2D Digital Filter, Azimuthal Component

The preferred embodiment of the FIR azimuthal filter 10 is shown in FIG.3. The azimuthal filter 10 uses lookup tables to provide readyprogrammability such that the filter response characteristics of theazimuthal filter 10 can readily be changed by the filter logic block 14.The use of look-up tables in the architecture of this filter providesfor a broad range of functionality.

In its simplest form, the filter 10 is configured as a linear 4-tap FIRfilter, with tap weights

    -α,0.5+α,0.5+α,+α.

where α is a real number between -0.5 and +0.5. (This notation indicatesthat the data on the two outer lines are multiplied by -α, while thedata on the two inner lines are multiplied by 0.5+α.) A 3-tapconfiguration is easily obtained by placing the two inner taps on thesame scan line, which gives tap weights of

    -α,1+2*α,-α.

To configure the filter 10 for linear operation, the output of lookuptable T21 is made proportional to α and passed to lookup tables T31,T32, and T33. Tables T31 and T32 linearly scale the amplitude of theouter lines by a factor equal to -α, and their outputs are averagedtogether by lookup table T41. Data from the inner lines are averagedtogether by lookup table T11, and scaled (by a factor equal 1+2*α) bylookup table T33. Inner and outer data are then summed and scaled bylookup table T51 to produce the filtered result.

Range and line number dependence of α is obtained using lookup tableT12. In the preferred embodiment, the value of α is specified at each of8 depths on the center line and on the edge lines. Linear interpolation,first in azimuth, and then in range, fills in the value of α at allother ranges and line numbers. The output of lookup table T12 is passedto lookup table T21.

If the filter is intended to function linearly, then T21 is simply theidentity map, i.e., its output is identical to its input from T12. Toactivate nonlinear behavior, T21 is configured such that the value of αderived from T12 is added to a term that depends on the output of T11,the average inner tap amplitude. In the preferred embodiment, thisdependence is given by a piecewise linear curve specified at 16amplitude levels evenly spaced between 0 and 255 (for 8 bit data).

Another form of nonlinearity can be obtained by configuring T11 toyield, in place of the average of its two input values, the root meansquare or the maximum. The same functionality is also possible with T41.

The elements 60-67 of FIG. 3 correspond closely to the similarlynumbered elements of FIG. 8 of the above-identified Hedberg patent, andthe corresponding portions of the Hedberg patent should be referencedfor a more detailed description of these components.

The filter control block 12 specifies the following parameters forcontrol of the azimuthal filter 10: the number of taps (3 or 4), thenumber of skipped lines between inner and outer taps and between the twoinner taps for the 4 tap case, the functionality of T11 and T41(average, max or rms), up to 8 depths and corresponding values of α forcenter and edge lines, 16 evenly spaced values of the piecewise linearfunction that determines the filter's nonlinearity, and the maximumvalue of a for all possible input amplitudes and spatial locations. Thefilter control block 12 passes all these parameters to azimuthal filterlogic 14, which computes and loads each of the lookup tables.

It will be recognized by those skilled in the art that it is possible toparametrize the azimuthal filter nonlinear and spatial dependence inmany other ways without any change in the fundamental functionality ofthe filter.

2D Digital Filter, Range Component

FIG. 4 of the present specification shows a block diagram of thepreferred embodiment of the digital range filter 11. Data from theazimuthal filter are clocked through a programmable gross delay block100 and programmable tap delay blocks 101, 102, 103. The programmablegross delay block 100 permits alignment in time between the digitalrange filter output and other signal paths. The programmable tap delayblocks 101, 102, 103 permit either 3-tap or 4-tap operation. Data on theouter taps are averaged in the outer computed programmable logic block105. For four tap operation, data on the inner taps are averaged in theinner computed programmable logic block 104. (For three tap operation,block 104 ignores the input from tap delay 102, and simply passes theinput from tap-delay 101 on as its output.) The results from blocks 104and 105, denoted Z_(in) and Z_(out), respectively, are presented to anoutput lookup table 106, which weights and sums the contributions fromthe inner and outer taps.

In its 4-tap configuration, the filter tap weights are

    -β,0.5+β,0.5+β,-β,

and for 3 taps, the filter tap weights are

    -β,1+2*β,-β.

Here the parameter β characterizes the response of the range filter 11in a manner analogous to the role that a plays for the azimuthal filter.To obtain these weights, the output lookup table 106 maps input dataZ_(in) and Z_(out) to

    2*((0.5+β)*Z.sub.in -β*Z.sub.out).

The factor of 2 in this expression results from the fact that Z_(in) andZ_(out) are averages of the inner and outer tap data.

To obtain nonlinear behavior, β is itself made dependent on Z_(in). Inthe preferred embodiment, this dependence consists of a piecewise linearfunction specified at 16 values of Z_(in) evenly spaced between 0 and255. This is similar to the parameterization described above for theazimuthal filter nonlinearity.

The outer computed programmable logic block 105 can be configured totake the maximum of the inputs from each outer tap, rather than theaverage. Similarly, the inner computed programmable logic block 104 canbe configured to take the maximum of the inner tap data. This provides asecond type of nonlinearity for the range filter 11.

All of the delay blocks 100-103 are programmable as a multiple of afixed minimum tap delay, which is simply the inverse of the rate atwhich data is clocked through the filter. For example, with a clock rateof 20 MHz, the delays are programmed in integer multiples of 50 ns. Theclock rate is the rate at which data are read out of the image memory 6.

The frequency response of the filter is determined by the sampling rateof the A/D converter 5, not by the clock rate. This is because eachclock cycle produces an effective delay (from the standpoint of thedigitized data) of one sample at the A/D converter frequency. Therefore,if the A/D converter sampling rate is changed, as it may when depth ischanged or an image enlargement function is activated or deactivated,and if the filter configuration remains unchanged, then the frequencyresponse of the filter would scale by the same factor as the A/Dconverter sampling rate. In order to overcome this potential problem,the control block 12 changes the filter configuration when the A/Dsampling rate changes. For example, if the A/D sampling rate isdecreased from 10 MHz to 5 MHz while β is left unchanged in the digitalfilter, the filter control block 12 responds by decreasing the number ofinner and outer tap delays to one half of the previous value.

The digital range filter 11 is quite similar to the filter shown inFIGS. 4 and 5 of the above-identified Hedberg patent, which should bereferenced for a more detailed description of the operation of thisfilter.

The filter control block 12 specifies the number of taps (3 or 4), thenumber of unit delays for the gross delay block 100 and inner and outertap delay blocks 101-103, the mode (average or maximum) of the computedprogrammable logic blocks 104, 105, and 16 evenly spaced values of thepiecewise linear function that determines the nonlinearity of thefilter. The filter control block 12 passes all these parameters to rangefilter logic 15, which computes and loads the output lookup table 106and configures the delay blocks 100-103 and the inner and outer logicblocks 104, 105.

Other parameterizations are also possible which do not alter theunderlying functionality.

EXAMPLE

The spectral responses of the filters 4, 10 and 11 can be varied widelyby appropriately programming the respective components. FIG. 12 of theabove-identified Hedberg patent illustrates the variety of linear videofilter spectral responses that are possible for a particular tap spacingand range of the parameter α.

By making a number of such plots in both azimuth and range, andselecting appropriate combinations, it is possible to implement filterswhich meet desired bandwidth criteria. A simple hypothetical example ofa design that ties together the analog and digital range filters 4, 11follows.

Consider an enlarged image with the following properties:

depth of top of image: 40 mm;

depth of bottom of image: 180 mm;

range of scan angles: 0 to 20 degrees on each side of center line;

number of pixels in image at center line: 220;

center frequency: 2.5 MHz;

N_(max) 2048;

Available A/D rates 20 MHz, 10 MHz, 5 MHz.

The vertical pixel density _(V) is 1.57 pixels/mm. The maximum axialfrequency displayable without aliasing is c*_(V) *cos(θ)/4, or

0.605 MHz at 0 degrees and 0.569 MHz at 20 degrees. Ideally, all spatialcomponents at frequencies greater than these values (at 0 and 20degrees, respectively) should be removed by filtering. To illustratethis hypothetical example, these frequencies are treated as the desired6 db bandwidths at 0 and 20 degrees. Other, more restrictive criteriaare possible (12 dB or 20 dB bandwidths, for example), and would resultin a further reduction of aliased spectral energy.

The sampling rate of this situation must not exceed c*N_(max) /(2*FOV),which is

11.264 MHz.

Hence, the sampling rate is 10 MHz, and each unit digital tapcorresponds to a delay of 100 ns. Configure the 3-tap analog videofilter with

α=-0.3

tap spacing=440 ns

gain multiplier=constant (linear filter configuration)

angle dependence vary with cos(θ),

and the digital axial filter with

number of taps=4

number of inner unit tap delays=5 (i.e., 500 ns)

number of outer unit tap delays=5 (i.e., 500 ns)

mode=average (for linear filter configuration)

β=0.25.

The spectral response for these filters is shown in FIGS. 5a-5c. FIG. 5ashows the response of the analog axial filter 4, FIG. 5b the response ofthe digital axial filter 11, and FIG. 5c the response of the two inseries. From FIG. 5c, the response at 0.605 MHz is down about 6 db, asdesired.

An analogous process may be used to construct the azimuthal filterdesign for the filter 10.

The filter in this simple example was designed solely to reduce aliasingartifacts. Such a filter is suitable for an edge enhancement controlsetting that yields a relatively "sharp" image. At other positions ofthe edge enhancement control setting, greater smoothing (lower α and β)would be desirable to suit a wide range of preferences in imageaesthetics.

Nonlinear behavior can also be incorporated into the design to producegreater smoothing at lower amplitude to reduce noise and improvecontrast resolution, as discussed in the above-identified Hedbergpatent.

From the foregoing, it should be apparent that an improved ultrasoundimaging system has been described in which the receive signal processingpath includes one or more filters and an A/D converter, and wherein atleast one filter parameter is selected as a function of the samplingrate of the A/D converter and an azimuthal line density characteristic.In the foregoing example the receive signal processing path includes theA/D converter 5 and the filters 4, 10 and 11. The filter control block12 operates as a means for selecting the filter parameters as a functionof the A/D sampling rate and the azimuthal line density characteristic.The filter parameters that are selected as a function of the samplingrate can control either or both of a range filter 4, 11 or an azimuthalfilter 10. The filter can be disposed either upstream of the A/Dconverter 5 (as is the filter 4) or downstream of the AND converter 5(as are the filters 10 and 11). The filter parameters may further beselected as a function of the vertical and/or horizontal pixel densityof the monitor 9.

It should also be clear that a method has been described for processinganalog receive signals. In particular, these receive signals arefiltered and converted to digital receive signals. The filter controlblock 12 modifies the filtering of the receive signals in response tochanges in the A/D sampling rate as well as in response to changes inthe azimuthal line density.

As used herein, the following terms are intended to have the followingmeanings, unless indicated otherwise by the context. The term "receivesignal" is used broadly to encompass both analog and digital signalsthat vary in response to ultrasonic energy sensed by a transducer, priorto scan conversion. Thus, signals at all of the various processingstages between the transducer T and the scan converter 8 are consideredto be receive signals.

An element is said to operate as a function of a variable when theoutput of the element varies in accordance with the variable, whether ornot the output of the element also varies in accordance with othervariables. In many cases an element will provide an output that variesas a function of several separate variables. In this case, the elementis said to operate as a function of each of the variables. For example,the filter control block selects filter parameters as a function of theA/D sampling rate, even though the particular filter parameters that arechosen at any given time also vary as a function of the other inputsignals to the control block discussed above.

The term "filter parameter" is intended broadly to encompass anycharacteristic of a filter such as filter response, bandwidth, degree ofnonlinearity, or any of the other parameters of the filters describedabove.

It should be understood that many changes and modifications can be madeto the preferred embodiment described above. For example, anyappropriate analog or digital filter can be substituted for the variousfilters described above. These filters can be implemented in anysuitable technology, and digital filters are not limited to filtersutilizing the lookup table techniques described above. In the simplestcase, there may simply be several parallel filters that can be switchedinto or out of the processing path. This invention is not limited to usewith FIR filters, but can readily be adapted for any desired type offilter.

Furthermore, the filter control block may use any suitable technology toselect filter parameters as a function of appropriate inputs. In thesimplest case, the filter control block can control switches that routethe receive signals to the filters having the desired properties.

Additionally, this invention can readily be adapted for use inultrasonic image systems which employ a digital beamformer, and whichplace the A/D converter upstream of the beamformer in the receive signalprocessing path.

It is therefore intended that the foregoing detailed description beregarded as illustrative rather than limiting, and that it be understoodthat it is only the following claims, including all equivalents, whichare intended to define the scope of this invention.

We claims:
 1. In an ultrasound imaging system comprising an ultrasonictransducer operative to generate receive signals indicative of sensedultrasonic energy, a receive signal processing path responsive to thereceive signals, and a scan converter responsive to the receive signalprocessing path, the improvement wherein said receive signal processingpath comprises:an analog detector; an A/D converter characterized by aselectable sampling rate and operatively connected to an output of theanalog detector; at least one filter characterized by at least onefilter parameter; and means for selecting the at least one filterparameter as a function of the sampling rate.
 2. The invention of claim1 wherein the filter comprises a range filter.
 3. The invention of claim1 wherein the filter comprises an azimuthal filter.
 4. The invention ofclaim 1 wherein the filter is disposed upstream of the AND converter inthe receive signal processing path.
 5. The invention of claim 1 whereinthe filter is disposed downstream of the A/D converter in the receivesignal processing path.
 6. The invention of claim 1 wherein the imagingsystem further comprises a display responsive to an output signal fromthe scan converter wherein said display is characterized by a pixeldensity, and wherein the selection means further selects the filterparameter as a function of the pixel density.
 7. A method for processinganalog receive signals generated by an ultrasonic transducer of anultrasonic imaging system prior to scan conversion, said methodcomprising the following steps:(a) generating analog video signals withan analog detector; (b) converting the analog video signals to digitalreceive signals at a selected sampling rate; (c) filtering at least oneof the analog video signals and the digital receive signals; (d)modifying the filtering step (b) in response to a change in the samplingrate; and (e) applying a filtered signal responsive to the filteringstep (b) to a scan converter.
 8. The method of claim 7 wherein thefiltering step comprises range filtering.
 9. The method of claim 7wherein the filtering step comprises azimuthal filtering.
 10. Theinvention of claim 7 wherein the converting step precedes the filteringstep in a receive signal processing path.
 11. The invention of claim 7wherein the filtering step precedes the converting step in a receivesignal processing path.
 12. The invention of claim 7 wherein themodifying step further comprises the step of modifying the filteringstep in response to a pixel density characteristic of the ultrasonicimaging system.